LED Photosensor

It is not always necessary to use special photoresistors or phototransistors to make light-sensitive switches. Although it is not well known, normal visible-light and infrared LEDs will also work. A voltage that depends on the intensity of the natural or artificial illumination falling on the LED can be taken from the anode of the LED. This behaviour can be easily verified by connecting a DVM or oscilloscope directly to the two leads of the LED.

Circuit Diagram:

LED Photosensor-Circuit Diagram

LED Photosensor Circuit Diagram

Since the load on the photoelectric potential should be kept as small as possible, a JFET is used here as a buffer. The type used is not critical; similar transistors should work equally well. The buffered voltage is fed to the inverting input of comparator IC1. The threshold voltage can be adjusted to meet the desires of the user by means of the potentiometer. A pull-up resistor is connected to the com-parator output, since the LM393 has an open-collector out-put. The supply voltage may be chosen anywhere in the range of 5 to 9 V.

Copyright : Elektor

Wire Loop Game

In the ‘Wire Loop Game’, a test of dexterity,  the player has to pass a metal hoop along a  twisted piece of wire without letting the hoop  touch the wire. Usually all the associated electronics does is ring a bell to indicate when the  player has lost. The version described here has  a few extra features to make things a bit more  exciting, adding a time limit to the game and a ticking sound during play.

Two 555 timer ICs are used to provide these  functions. IC1 is configured as a monostable which controls the time allowed for the  game, adjustable using potentiometer P1. IC2  is a multivibrator to provide the ticking and Two 555 timer ICs are used to provide these  functions. IC1 is configured as a monostable which controls the time allowed for the  game, adjustable using potentiometer P1. IC2  is a multivibrator to provide the ticking and he continuous buzz that indicates when the  player has touched the wire with the hoop.

Circuit diagram :

Wire Loop Game-Circuit Diagram

Wire Loop Game Circuit Diagram

When the monostable is in its steady state,  the output of IC1 (pin 3) is low. T1 acts as  an inverter, and D2 is thus forward biased.  R8 and R4 are therefore effectively in parallel, with the result that IC2 produces a low audible tone. The value of R4 is considerably  greater than that of R8, and so the frequency  of the buzz generated by IC2 is chiefly deter-mined by the value of R8.

When the monostable is triggered, the high  level at the output of IC1 is again inverted  by T1. D2 is reverse biased and so R8 is effectively removed from the circuit. The frequency of IC2 is now largely determined by  the value of R4. The ratio of R4 to R5 and the  value of C4 affect the mark and space periods for the multivibrator: for a satisfactory  ticking sound short pulses with long gaps  between work well.

Whether a sound is produced also depends  on the voltage on pin 4 of IC2. When the 9 V  supply is connected the monostable is initially inactive and there is no voltage across  C1. Pin 4 (reset) on IC2 is thus low and no tone  is produced. IC1 is activated by a brief press of  S1, which generates a low-going trigger signal  on pin 2 to start the game. C1 now charges via  D1 and IC2 is allowed to oscillate, generating  the ticking sound.

The pulse width of the monostable sets the  game duration, and can be adjusted using  P1. If the allowed time expires, or if the reset  input to IC1 is taken low (which happens when the hoop touches the wire), the monostable  returns to the quiescent state. This causes IC2  to generate the low buzz sound. D1 is now  reverse biased and C1 discharges through the  relatively high-valued resistor R9. After a few  seconds the voltage across C1 falls sufficiently  that the buzz stops and the circuit is ready for  the next player.

The circuit can be built first on a breadboard,  so that the component values can easily be changed to suit particular preferences for  game duration and buzz pitch. When suitable  values have been selected the circuit can be  built more permanently on a printed circuit  board. The author used a sheet of plywood  to form a base for the game, the twisted wire  being fixed to the board and wired to the electronics mounted below it.

Author: Andreas Binner - Copyright:Elektor

Equalising HEXFETs

When experimenting with audio output  stages featuring multiple HEXFETs it quickly  becomes apparent that the total power is  not divided equally among the individual transistors.

The reason for this lies in the wide part-to-part variations in gate-source voltage, which  in the case of the IRFP240 (or IRFP9240) can  be from 2 V to 4 V. Source resistors in the  region of 0.22 Ω as commonly seen in amplifier circuits (see example circuit extract) help  to counteract this, but usually not to a sufficient extent.

Equalising HEXFETs Circuit

One possible solution to this problem is to ‘select’ the transistors used so that their gate-source voltages match as closely as possible.  For building prototypes or very short production runs this is feasible, but requires additional manual effort in testing the components, and, of course, more transistors mus be ordered than will finally be used.

The circuit idea shown here allows differences  in gate-source voltage between pairs of transistors to be compensated for by the addition of trimmer potentiometers: the idea has been tested in simulation using Simetrix. The  second circuit extract shows the required  changes.

Author : Alfred Rosenkränzer - Copyright : Elektor

Battery-powered Headphone Amplifier

Low distortion Class-B circuitry 6V Battery Supply

Some lovers of High Fidelity headphone listening prefer the use of battery powered headphone amplifiers, not only for portable units but also for home "table" applications. This design is intended to fulfil their needs and its topology is derived from the Portable Headphone Amplifier featuring an NPN/PNP compound pair emitter follower output stage. An improved output driving capability is gained by making this a push-pull Class-B arrangement. Output power can reach 100mW RMS into a 16 Ohm load at 6V supply with low standing and mean current consumption, allowing long battery duration. The single voltage gain stage allows the easy implementation of a shunt-feedback circuitry giving excellent frequency stability.

Circuit diagram :

Battery-powered Headphone Amplifier Circuit diagram

Battery-powered Headphone Amplifier Circuit diagram

Notes:

  • For a Stereo version of this circuit, all parts must be doubled except P1, SW1, J2 and B1.
  • Before setting quiescent current rotate the volume control P1 to the minimum, Trimmer R6 to maximum resistance and Trimmer R3 to about the middle of its travel.
  • Connect a suitable headphone set or, better, a 33 Ohm 1/2W resistor to the amplifier output.
  • Switch on the supply and measure the battery voltage with a Multimeter set to about 10Vdc fsd.
  • Connect the Multimeter across the positive end of C4 and the negative ground.
  • Rotate R3 in order to read on the Multimeter display exactly half of the battery voltage previously measured.
  • Switch off the supply, disconnect the Multimeter and reconnect it, set to measure about 10mA fsd, in series to the positive supply of the amplifier.
  • Switch on the supply and rotate R6 slowly until a reading of about 3mA is displayed.
  • Check again the voltage at the positive end of C4 and readjust R3 if necessary.
  • Wait about 15 minutes, watch if the current is varying and readjust if necessary.
  • Those lucky enough to reach an oscilloscope and a 1KHz sine wave generator, can drive the amplifier to the maximum output power and adjust R3 in order to obtain a symmetrical clipping of the sine wave displayed.

Technical data:

Output power (1KHz sinewave):
    16 Ohm: 100mW RMS
    32 Ohm: 60mW RMS
    64 Ohm: 35mW RMS
    100 Ohm: 22.5mW RMS
    300 Ohm: 8.5mW RMS
Sensitivity:
    160mV input for 1V RMS output into 32 Ohm load (31mW)
    200mV input for 1.27V RMS output into 32 Ohm load (50mW)
Frequency response @ 1V RMS:
    flat from 45Hz to 20KHz, -1dB @ 35Hz, -2dB @ 24Hz
Total harmonic distortion into 16 Ohm load @ 1KHz:
    1V RMS (62mW) 0.015% 1.27V RMS (onset of clipping, 100mW) 0.04%
Total harmonic distortion into 16 Ohm load @ 10KHz:
    1V RMS (62mW) 0.05% 1.27V RMS (onset of clipping, 100mW) 0.1%
Unconditionally stable on capacitive loads

Source : red circuits

Slave Flash for Underwater Camera

The flash module in this circuit comes from a  Fuji disposable camera. The author’s design  is based on various ideas on this subject that  can be found on the Web. The guide number  [1] of the flash is approximately 14 in the air  and close to 6 underwater. The flash intensity  is not adjustable.

Slave Flash for Underwater Cameraqq

This flash unit is primarily intended to be used  for underwater photography, which is why  the author fitted it in a  case originally used for  a Nikon Coolpix 7900.  Of course, it can also  be used for dry-land  photography. The flash  module is powered by  a 1.5-V battery, which  must supply approximately 30 to 40 mA  to charge the capacitor. The control portion is built around a  PIC12F675, which is  powered by a 3-V button cell. Its current consumption is practically negligible  just a few  milli amperes while the flash is active and only  600 nA the rest of the time, when the micro-controller is in the standby state. For this rea-son, the unit does not have an on/off button. The flash from the Fuji camera is triggered by  a mechanical contact that is actuated at the  same time as the camera shutter. Here this  contact is replaced by an MCR-100-8 thyristor with a 1-kΩ resistor in series with the gate.  These two components are fitted directly on  the Fuji flash module.

Slave Flash for Underwater Camera Circuit Diagram

There are many different types of disposable  camera, each with its own type of flash module. However, these modules are all similar,  so you can easily adapt the design described  here to whatever type you can put your hands  on. Pay attention to the voltages, and don’t forget to connect the grounds of the flash  PCB and the logic circuitry together. Schematics for many of these flash modules are  often available on the Web, so it shouldn’t be  difficult to find something close to what you  actually have.

The firmware [2] has three operating modes:  manual, pseudo-TTL (through the lens,  which means that the light level is measured  through the lens) and sleep. In manual mode the flash it triggered when you press the shutter button. In pseudo-TTL mode there are a  few short flashes before the main flash (commonly used for red-eye reduction). The number of pre-flashes varies from one camera  to the next, and even from one shot to the  next. In pseudo-TTL mode, the firmware gets  around this problem by waiting for 100 ms  after the first flash before it tries to detect  the exposure flash. LED D1 lights up if the pre-flash has been detected  but the main flash has  not been detected after  the 100-ms delay.

The contribution of the  slave flash to the expo-sure of the subject is not  included in the measurement made by the  camera, but instead  simply adds to the light  from the master flash –  hence the designation  ‘pseudo-TTL’. Although  the author considered  the option of a true  TTL design, or at least  adjustable flash intensity, this requires a very  specific transistor (25AAJ8 or equivalent) that  is very difficult to obtain.

Author : Daniel Savel  – copyright : Elektor